Fig 1. A MicroZed Board

The AXI bus has become prominent as a defacto standard for working with either Xilinx or Intel supplied IP cores. This common standard is intended to make it easy to interface a design to one of a variety of System on a Chip cores, such as Xilinx’s MicroBlaze or Intel’s NiosII. The bus is also used by ARM, and so it is a natural fit for both Zynq and Soc+FPGA products.

While this is all well and good, AXI is a beast to work with. Achieving both correct performance, as well as high speed performance, can be a challenge. Today, we’ll limit ourselves to the AXI-lite bus: a version of AXI that supports neither bursts, nor locking, nor transaction ID’s, nor varying quality of service guarantees. While I’d like to imagine that these simplifications have made it easy enough for a beginner to be able to work with it, I would have to imagine that most beginners who have tried to work with the AXI-lite protocol used by either the Zynq or Soc+FPGA chips haven’t found it to be the simple protocol they were hoping for.

It has certainly been anything but simple for me.

Today, let’s take a look at how you can use a set of formal properties to work with an AXI-lite slave–both to verify that it works as well as to query how well it works. Along the way, I’ll demonstrate how easy it us to use this set of formal properties to find the problems in an AXI-lite slave implementation.

The AXI-lite Bus

Some time ago, I wrote an article describing how to build a simple wishbone peripheral.A simple wishbone peripheral only needed to respond to a request,

always @(posedge i_clk)
if ((i_wb_stb)&&(!o_wb_stall)&&(i_wb_we))
	some_data[i_wb_addr] <= i_wb_data;

an acknowledgment,

always @(posedge i_clk)
	o_wb_ack <= (!i_reset)&&(i_wb_stb)&&(!o_wb_stall);

some returned data,

always @(posedge i_clk)
	o_wb_data <= some_data[i_wb_addr];

and a (never) stall signal.

assign	o_wb_stall = 1'b0;

Voila! That’s all the signaling required for a basic Wishbone peripheral.

If only AXI were as easy.

Fig 2. The AXI bus is composed of five separate channels

Instead of one read-write request channel, and one acknowledgment-response channel, AXI has five such channels. For writing values to the bus, there’s the write address channel, the write data channel, and the write response channel. For reading values from the bus, there’s a read address-request channel and a read response channel.

For today, let’s just discuss the AXI-lite version of this interface. Unlike the full AXI specification, AXI-lite removes a lot of capability from this interaction. Perhaps the biggest differences are that, with AXI-lite, any read and write request can only reference one piece of data at a time, and that there is no need to provide unique identifiers for each transaction. There are other more minor differences as well. AXI-lite has no requirement to implement locking, quality of service, or any cache protocols. Once these differences are accounted for, AXI-lite becomes almost as easy to verify as a Wishbone (WB) transaction.

Don’t get me wrong, building an AXI-lite peripheral is still a challenge, but verifying an AXI-lite peripheral? Not so much.

The key to these transactions are the various *READY and *VALID signals. *VALID is used to signal a valid request or acknowledgment. The two signals together form a handshake. One side of the channel will set a valid signal when it has information to send, whether request or acknowledgment, while the other side controls a ready signal. You may recognize this from our prior discussion of the simple handshake method of pipeline control. The AXI specification also contains a very specific requirement: asserting the valid signal can never be dependent upon the ready signal for the same channel.

Perhaps you may remember with the WB specification that it takes a hand shake to make a bus request. Both STB (from the master) and !STALL (from the slave) must be true in order for a request to be accepted. The same is basically true of AXI only the names have changed: *VALID and *READY must be true for a bus request to be accepted by the slave. This *VALID signal is similar to the WB STB signal, while *READY is similar to the !STALL signal.

However, unlike WB, AXI has separate channels for reading and writing, and each of these channels has its own VALID and READY signal set. AXI also requires a VALID and READY handshake on acknowledgments, both for read and separately for write acknowledgments.

AXI-lite Read

Perhaps it might make sense to walk through an example or two. Fig. 2 therefore shows several example AXI-lite read transactions from the perspective of the slave. In this example, I’ve chosen to use Xilinx’s convention where the AXI signals are in all capitals, although this loses the i_* and o_* prefix that I enjoy using to indicate which signals are inputs and which are outputs. (We’ll switch back later, when we get to the formal property set.)

Fig 2. Several AXI-lite read transactions

Each request starts with the AXI-lite master raising the S_AXI_ARVALID signal, signaling that it wants to initiate a read transaction. Together with the S_AXI_ARVALID signal, the master will also place the address of the desired read on the bus.

The slave will respond to this request by raising the S_AXI_ARREADY signal, although the specification sets forth several comments about this. For example, the slave can set S_AXI_ARREADY before or in response to the S_AXI_ARVALID signal. Further, all the AXI outputs are not allowed to be dependent combinatorially on the inputs, but must instead be registered. Beyond that, the slave can stall the bus as required by the implementation.

A read transaction request takes place when both S_AXI_ARVALID and S_AXI_ARREADY are true on the same clock.

Looking back at Fig 2, you can see four such read transaction requests being made.

As with the transaction requests, the acknowledgments also only take place when S_AXI_RVALID and S_AXI_RREADY, the signals from the acknowledgment channel, are both true. Because responses must be registered, the earliest the slave can acknowledge a signal is on the clock following the request.

Let’s now turn our attention to the acknowledgments shown in Fig 2. In this example, the slave acknowledge the request on the clock after the request is made. Since the master holds S_AXI_RREADY high, the acknowledgment only needs to be high for one transaction. Further, in addition to S_AXI_RVALID, the slave will also set S_AXI_RDATA, the result of the read, and S_AXI_RRESP, an indicator of any potential error conditions. As with the S_AXI_ARADDR signal above, these two signals are part of the acknowledgment transaction as well.

The more interesting transaction may be the high speed transaction shown at the end of the trace in Fig 2. Judging from this transaction, if the master wishes to transmit at its fastest speed, this particular core will only ever support a rate of one request every other clock.

Working from the spec, just a couple of formal verification properties will help keep us from running into problems. From what we’ve learned examining the figures above, the following basic properties would seem prudent.

  1. Once S_AXI_ARVALID is raised, it must remain high until S_AXI_ARVALID && S_AXI_ARREADY

  2. While S_AXI_ARVALID is true but the slave hasn’t yet raised S_AXI_ARREADY, S_AXI_ARADDR must remain constant.

  3. Similarly, once the S_AXI_RVALID reply acknowledgment request is raised, it must also remain high until S_AXI_RVALID && S_AXI_RRESP are both true.

  4. As with the read address channel, while S_AXI_RVALID is true and the master has yet to raise S_AXI_RREADY, both S_AXI_RDATA and S_AXI_RRESP must remain constant.

  5. For every request with S_AXI_ARVALID && S_AXI_ARREADY, there must follow one clock period sometime later where S_AXI_RVALID && S_AXI_RREADY.

    Unlike our development of the WB properties, there is no bus abort capability in the AXI bus protocol. As a result, following a bus error, you’ll still need to deal with any remaining acknowledgments.

  6. Just to keep things moving, we’ll also want to insist that after some implementation defined minimum number of clock ticks waiting the slave must raise S_AXI_ARREADY.

  7. The same applies to the reverse link: the master should not be allowed to hold S_AXI_RREADY low indefinitely while S_AXI_RVALID is high.

We’ll add a couple more properties beyond these below, but for now these should suffice to capture most of what AXI-lite requires.

That’s how reads work, so let’s now go on and examine the write path.

AXI-lite Write Example

While the AXI read channel above may appear to be straightforward, the write channel is anything but. The write address channel is designed to allow a single “burst” request to indicate a desire to write to multiple addresses, closely followed by a burst of data on the write data channel. AXI-lite, unlike the full AXI protocol, has no burst write support. Every address request must be accompanied by a single piece of associated write data. To make matters worse, the two channels are only loosely synchronized, forcing the slave to synchronize to them internally.

Were S_AXI_AWVALID tied to S_AXI_WVALID, and S_AXI_AWREADY tied to S_AXI_WREADY, the slave’s write channel logic would collapse into the basic read problem discussed above. Alas, this is not so. The AXI-lite slave is thus forced to try to synchronize these two channels in order to make sense of the transaction.

Fig. 3 shows a basic set of write transactions illustrating this problem.

Fig 3. Some example write transactions

The first three transactions within Fig. 3 shows the bounds set on the synchronization of the channels. Note that I found these bounds within Xilinx’s documentation. They are not present in the specification itself, as far as I can tell. Since they simplify the problem significantly, I’ve chosen to implement them as part of this property set.

Let’s look at and discuss each of the transactions shown in Fig. 3 above.

  1. The first transaction is as simple as one might like. Both write address and write data requests show up at the same time. On the following clock the respective *WREADY signals are set, and then the acknowledgment takes place on the third clock where *BVALID is set.

    Let’s note two things about this picture. First, the *WREADY signals are kept low until the request is made. This is not required of the bus and in general slows the bus down. Second, the S_AXI_BREADY signal is held high. The particular core we are demonstrating will fail if this is not the case. We’ll come back to that in a moment.

  2. The second transaction illustrates one of the bounds on the write channels: Xilinx’s rules allow the write address valid signal to show up no more than two clocks before the write data. In this example, the slave holds the two *WREADY lines low until the clock after both are valid.

  3. The third transaction illustrates the other bound: the write data channel may arrive up to one clock before the write address channel. As with the previous example, this slave holds the various *WREADY lines low until both are present. The acknowledgment then takes place on the next clock.

  4. The final three transactions are part of a speed test measuring how fast this core can handle subsequent transactions. In the case of this slave, the slave waits until both S_AXI_AWVALID and S_AXI_WVALID signals are high before raising the ready signal. This wait period limits the speed of this slave core to one transaction every two clocks.

    If the Lord wills, I’d like to also present another AXI-slave core with much better throughput performance, but that will need to remain for another day.

This protocol suggests a couple formal properties.

  1. Each of the *VALID signals should remain high until their respective *READY signal is also high. This applies to both the write address channel, the write data channel, as well as the acknowledgment channel.

  2. The data associated with each channel should be constant from when the *VALID signal is set until both *VALID and *READY are set together.

  3. We also discussed the two Xilinx imposed limits above as well.

    – The write data channel may become active no more than one clock before the write address channel, and

    – The write address channel may become active no more than two clocks before the write data channel.

  4. Finally, there should be no more than one acknowledgment per write request. Well, it’s a bit more complex than that. Both write address and write data channels will need to be checked, so that there is never any write acknowledgment until a request has previously been received on both of those two channels.

Using a Formal Property Set

Further on in this article, we’ll dive into the weeds of how to express the formal properties necessary to specify an AXI-lite bus interaction. For now, I’d like to discuss what you can do with such a formal property set.

I currently have Vivado 2016.3 installed on my computer. Is it out of date? Yes. However, it works for me. Xilinx has had problems breaking things when they make updates, so I hesitate to update Vivado lest I break something that is already working.

That said, this video from Xilinx describes how to create an AXI-lite peripheral core. I followed similar instructions, and received a default demonstration AXI-lite peripheral.

I then added a formal property section to the bottom of this core.

////////////////////////////////////////////////////////////////////////////////
//
// Formal Verification section begins here.
//
// The following code was not part of the original Xilinx demo.
//
////////////////////////////////////////////////////////////////////////////////
`ifdef	FORMAL

The important part of this property section is the reference to our formal AXI-lite property file. Since the properties require some counters in order to make certain that exactly one response is given to every transaction, let’s set a width for those counters and declare them here.

	localparam	F_LGDEPTH = 4;

	wire	[(F_LGDEPTH-1):0]	f_axi_awr_outstanding,
					f_axi_wr_outstanding,
					f_axi_rd_outstanding;

For this particular design, a four bit counter is really overkill, but it will work for us.

Then, we connect the various signals associated with the AXI-lite protocol to our core. The parameters have fairly well defined meanings. The data width is the number of data bits in the bus. The address width is the number of bits required to describe a single octet in the data stream. This is different from WB, which has only the number of bits necessary to describe a word address. We’ll ignore the extra bits for now, since they are fairly irrelevant here.

	//
	// Connect our slave to the AXI-lite property set
	//
	faxil_slave #(  .C_AXI_DATA_WIDTH(C_S_AXI_DATA_WIDTH),
			.C_AXI_ADDR_WIDTH(C_S_AXI_ADDR_WIDTH),
			.F_LGDEPTH(F_LGDEPTH)) properties(
		.i_clk(S_AXI_ACLK),
		.i_axi_reset_n(S_AXI_ARESETN),
		//
		.i_axi_awaddr(S_AXI_AWADDR),
		.i_axi_awcache(4'h0),
		.i_axi_awprot(S_AXI_AWPROT),
		.i_axi_awvalid(S_AXI_AWVALID),
		.i_axi_awready(S_AXI_AWREADY),
		//
		.i_axi_wdata(S_AXI_WDATA),
		.i_axi_wstrb(S_AXI_WSTRB),
		.i_axi_wvalid(S_AXI_WVALID),
		.i_axi_wready(S_AXI_WREADY),
		//
		.i_axi_bresp(S_AXI_BRESP),
		.i_axi_bvalid(S_AXI_BVALID),
		.i_axi_bready(S_AXI_BREADY),
		//
		.i_axi_araddr(S_AXI_ARADDR),
		.i_axi_arprot(S_AXI_ARPROT),
		.i_axi_arcache(4'h0),
		.i_axi_arvalid(S_AXI_ARVALID),
		.i_axi_arready(S_AXI_ARREADY),
		//
		.i_axi_rdata(S_AXI_RDATA),
		.i_axi_rresp(S_AXI_RRESP),
		.i_axi_rvalid(S_AXI_RVALID),
		.i_axi_rready(S_AXI_RREADY),
		//
		.f_axi_rd_outstanding(f_axi_rd_outstanding),
		.f_axi_wr_outstanding(f_axi_wr_outstanding),
		.f_axi_awr_outstanding(f_axi_awr_outstanding));

If we wanted to stop here and only run a bounded model check, we could do that. However, with just a couple of more properties we can make certain this design will pass induction as well–or not, as we’ll see in a moment.

For example, this core will only ever allow a single transaction. Further, once that transaction request has been made, but before the acknowledgment, the appropriate acknowledgment valid flag will be high. Not only that, but when the acknowledgment valid flag is high is the only time we’ll have one pending transaction.

	always @(*)
	if (S_AXI_ARESETN)
	begin
		assert(f_axi_rd_outstanding == ((S_AXI_RVALID)? 1:0));
		assert(f_axi_wr_outstanding == ((S_AXI_BVALID)? 1:0));
	end

Likewise, this core does not allow the number of outstanding requests on the write address channel to differ at all from those on the write data channel.

	always @(*)
		assert(f_axi_awr_outstanding == f_axi_wr_outstanding);

Then, we create a very simple SymbiYosys script:

[tasks]
cvr
prf

[options]
cvr: mode cover
cvr: depth 60
prf: mode prove
prf: depth 40

[engines]
smtbmc

[script]
read -formal xlnxdemo.v
read -formal faxil_slave.v
prep -top xlnxdemo

[files]
xlnxdemo.v
faxil_slave.v

This script describes two tasks. One task, named cvr, will check the cover properties in this core. Since we haven’t introduced any yet, we’ll come back to this task in a moment. The second task, prf, will attempt to formally verify that this core meets all of the properties required of any AXI-lite protocol core–basically all of the properties mentioned above.

Now, when we run SymbiYosys to check the safety properties (i.e. the assertions),

% sby -f xlnxdemo.sby prf

The proof fails almost immediately.

This first problem comes from the fact that none of the various signal registers are given appropriate initial values. While I personally consider this to be a bug, many individuals will consider this irrelevant in a core that depends upon a reset like this one does. Therefore, let’s just quietly fix the core with some initial statements and go on.

	// The following lines are only questionable a bug
	initial	axi_arready = 1'b0;
	initial	axi_awready = 1'b0;
	initial	axi_wready  = 1'b0;
	initial	axi_bvalid  = 1'b0;
	initial	axi_rvalid  = 1'b0;

And again the design fails. This time it fails with the trace shown in Fig. 4 to the right.

Fig. 4. Xilinx's demonstration code drops a write acknowledgment

In this image, you can see two write transactions. I’ve colored them with two different colors, to help separate the two and make this example easier to follow. The image differs, however, from our previous write example in Fig 3 above simply because the S_AXI_BREADY signal is not held high. As a result, the S_AXI_BVALID transaction is not immediately acknowledged until S_AXI_BREADY has been valid for a whole clock. By that time, however, the logic within the core has lost the reality that there is a second transaction that needs to be acknowledged as well. Hence, once the core drops the S_AXI_BVALID line, a transaction has been lost.

If we want to move on and look for other problems, we could bandage over this bug with an assumption. While you’d never want to do this in production code, sometimes it is helpful to move on in order to find some other problem. In this case, a simple assumption causes this error to go away.

	always @(*)
		assume(S_AXI_BREADY);

However, when we run the tools again the design still fails. Looking at the trace reveals that it is failing for the same basic bug again, only now the problem is found within the read channel, as shown in Fig 5.

Fig. 5. Xilinx's demonstration code drops a read acknowledgment

If we assume that S_AXI_RREADY is always high, just like we did with S_AXI_BREADY, this failure also vanishes and now the core can be verified for all time using induction.

With a little looking, and a quick trace capability, it doesn’t take long to chase down the bug. You can see the problem below as it exists for the S_AXI_ARREADY signal. Basically, the core allowed this signal to go high before it knew that the S_AXI_RVALID signal would be acknowledged.

If you page through the code, you’ll find the always block, shown below, that sets the axi_arready signal. It starts with a basic, almost boilerplate, reset function to clear axi_arready.

	always @( posedge S_AXI_ACLK )
	begin
	  if ( S_AXI_ARESETN == 1'b0 )
	    begin
	      axi_arready <= 1'b0;
	      axi_araddr  <= 7'b0;
	    end
	  else
	    begin

Early on in the operation, though, we find the bug. In particular, axi_arready is set irrespective of whether the result channel is stalled and there’s no place to hold the result.

	      if (~axi_arready && S_AXI_ARVALID)
	        begin
	          // indicates that the slave has acceped the valid read address
	          axi_arready <= 1'b1;
	          // Read address latching
	          axi_araddr  <= S_AXI_ARADDR;
	        end
	      else
	        begin
	          axi_arready <= 1'b0;
	        end
	    end
	end

Just a touch of extra logic will fix this for us.

	      if (!axi_arready && S_AXI_ARVALID && (!S_AXI_RVALID || S_AXI_RREADY))
	        begin
	          // indicates that the slave has acceped the valid read address
	          axi_arready <= 1'b1;
	          // Read address latching
	          axi_araddr  <= S_AXI_ARADDR;
	        end
	      else
	        begin
	          axi_arready <= 1'b0;
	        end
	    end
	end

A similar fix to the write channel and the design should pass nicely.

Cover

The check above encourages us that this design will not violate any of our safety properties, but will it work? Or, rather, how well can it be made to work? To answer that question, let’s create a cover() property.

Cover properties are known as liveness properties, versus the assertion properties which are known as safety properties. When a safety property fails, a trace is created showing how the property may be made to fail. However, when a safety property succeeds you know the assert() will always be valid and so no trace is created. Cover properties are the opposite. A cover property succeeds if there is at least one way to make the statement true. In that case, a trace is generated. More generally, one trace is generated for every cover() statement within a design, or the cover() check will fail.

Within the formal property set, there are two cover properties just to make certain the design is able to function. These properties verify that both a read and write operation are able to succeed using the core.

What I want to do now is to check performance, and we can use a cover property for that purpose.

Let’s see if we can retire four write instructions in four clocks.

	always @(posedge S_AXI_ACLK)
		cover( ((S_AXI_BVALID)&&(S_AXI_BREADY))
			&&(!$past((S_AXI_BVALID)&&(S_AXI_BREADY),1))
			&&( $past((S_AXI_BVALID)&&(S_AXI_BREADY),2))
			&&(!$past((S_AXI_BVALID)&&(S_AXI_BREADY),3)));

Let’s also test whether we can retire four read requests in four clocks as well.

	always @(posedge S_AXI_ACLK)
		cover( ((S_AXI_RVALID)&&(S_AXI_RREADY))
			&&(!$past((S_AXI_RVALID)&&(S_AXI_RREADY),1))
			&&( $past((S_AXI_RVALID)&&(S_AXI_RREADY),2))
			&&(!$past((S_AXI_RVALID)&&(S_AXI_RREADY),3)));

These two tests would be easier to express with concurrent assertions, such as:

	// Writes
	cover property (@(posedge i_clk)
		(S_AXI_BVALID)&&(S_AXI_BREADY) [*4]);

	// Reads
	cover property (@(posedge i_clk)
		(S_AXI_RVALID)&&(S_AXI_RREADY) [*4]);

Wow, those are nice to work with!

I personally like the four clock test, because sometimes there is a single stage within the design somewhere that can queue up an answer and so succeed on a two clock test. A four clock test on a design this simple will only succeed if the core can truly retire one instruction on every clock.

Not surprisingly, this test fails. This particular core is unable to handle a one transaction per clock throughput.

If high speed were your goal, then, you would say the core is crippled. (Yes, I have an alternative core if you want something that uses AXI-lite and yet has better performance.)

We could adjust the two tests and make them check for one instruction retiring on every other clock.

	// First a write check
	always @(posedge S_AXI_ACLK)
		cover( ((S_AXI_BVALID)&&(S_AXI_BREADY))
			&&($past((S_AXI_BVALID)&&(S_AXI_BREADY),2))
			&&($past((S_AXI_BVALID)&&(S_AXI_BREADY),4))
			&&($past((S_AXI_BVALID)&&(S_AXI_BREADY),6)));

	// Now a read check
	always @(posedge S_AXI_ACLK)
		cover( ((S_AXI_RVALID)&&(S_AXI_RREADY))
			&&($past((S_AXI_RVALID)&&(S_AXI_RREADY),2))
			&&($past((S_AXI_RVALID)&&(S_AXI_RREADY),4))
			&&($past((S_AXI_RVALID)&&(S_AXI_RREADY),6)));

This test now succeeds.

If you choose to examine the formal properties within the core, you’ll notice there is also a very large set of code at the bottom to set up two rather complicated cover traces. We’ve already reviewed the results of those complex cover statements in Figs. 2 and 3 above.

Exhaustive Coverage, Exponential Complexity

The first lesson of formal verification is that it is exhaustive. Every possible input, output, and register combination are checked to determine whether a property holds or not. As you might imagine, this creates an exponential explosion in complexity that can be hard to manage. This can often discourage a learner from trying formal methods in the first place.

To put that whole argument into perspective, know this: I have a series of not one or two but twelve separate AXI-lite proofs in my Wishbone to AXI bridge(s) repository. It takes me less than two minutes to formally verify all of these cores.

Finally, consider what we’ve done: for the price of a small insertion of code into our design, referencing a pre-written property set, and for the cost of only a handful of other core-specific properties, we’ve managed to find, fix, and then formally verify an AXI-lite core. After you’ve done this once or twice, you’ll find that the whole verification process takes only minutes to set up, and less than that to get your first trace. This makes it very easy for me, when I want to reply to someone’s request for help on either Xilinx’s or Digilent’s forums, to quickly review their code and provide a comment on it.

Fixing the code? Well, that can take more time.

So just what does this property set look like?

AXI-lite Properties

We’ve already discussed most of the properties above, all that remains now is to lay out the details and write the immediate assertions to accomplish these tasks. The basic properties were:

  1. Requests must wait to be accepted

  2. Acknowledgments can only follow requests

  3. All responses must return in a known number of cycles

  4. Waiting requests should not be held waiting more than some maximum delay

The first step in writing this property set will be to create several configuration parameters that can be used to configure the properties to match the needs of our design. Shown below is the AXI-lite slave property set, and the various configuration parameters within it.

The first configuration parameter is the width of the bus.

module faxil_slave #(
	// The width of the data bus
	parameter C_AXI_DATA_WIDTH	= 32,// Fixed, width of the AXI R&W data

While most of my work is done with a 32-bit bus, the property set should be generic enough to allow bus widths of other sizes, such as 8, 16, 64, or 128 bits. Why might you want 128 bits? Because many designs including DDR SDRAM’s can transfer 128-bits or more per clock.

Following the number of data bits, C_AXI_ADDR_WIDTH controls the number of bits used to describe an address within the peripheral. This needs to be a sufficient number of bits necessary to access every octet within the address space of the slave, even though we are going to ignore the sub-word address bits for now. (There’s only one requirement of them, associated with the S_AXI_WSTRB signal, and I haven’t coded that up yet.)

	parameter  C_AXI_ADDR_WIDTH	= 28,// AXI Address width (log wordsize)

Further, since I find C_AXI_DATA_WIDTH and C_AXI_ADDR_WIDTH rather cumbersome to type, I’m going to create two short-cut names: DW for the data bus width, and AW for the address width.

	localparam DW			= C_AXI_DATA_WIDTH,
	localparam AW			= C_AXI_ADDR_WIDTH,

Some implementations add AXI cache flags to the address request. These flags indicate whether the transaction is to be bufferable, non-bufferable, cachable, non-cachable, or more. I’m not personally using these flags. However, to handle both cores with and without these bits, we’ll use the parameter F_OPT_HAS_CACHE. If F_OPT_HAS_CACHE is set, the slave will assume particular values for i_axi_awcache and i_axi_arcache, indicating that the write is to be done to the cache or through the cache. This is probably more important for an AXI master than the slave, but since the two are mirrors of each other, we’ll keep it in here.

	parameter [0:0]	F_OPT_HAS_CACHE = 1'b0,

Sometimes I need to verify a write-only AXI interface, such as in this AXI-lite write-channel to wishbone bridge. In that case, I’ll want to assume the read channel is idle and remove the read channel cover check. F_OPT_NO_READS can be set to make this happen.

	parameter [0:0]	F_OPT_NO_READS  = 1'b0,

F_OPT_NO_WRITES is the analog to F_OPT_NO_READS. If F_OPT_NO_WRITES is set, then the proof will assume the write channel is idle, and remove the write channel cover check. This is used by my AXI-lite read-channel to wishbone bridge core.

	parameter [0:0]	F_OPT_NO_WRITES = 1'b0,

AXI defines three separate possible responses: an OK response, a slave produced an error response, or an interconnect produced an error response. If a particular slave cannot produce any form of bus error, it makes sense to disallow it. Clearing F_OPT_BRESP to zero will disallow any form of error on the write channel.

	parameter [0:0]	F_OPT_BRESP = 1'b1,
	//
	//  The same is true for F_OPT_RRESP for the read channel
	parameter [0:0]	F_OPT_RRESP = 1'b1,

Xilinx’s AXI reference guide requires a rather lengthy reset of 16 clock periods. If the slave (or master) being verified isn’t creating that reset, then it makes sense to just assume the reset is present. The F_OPT_ASSUME_RESET configures the core to do just that.

	parameter [0:0]	F_OPT_ASSUME_RESET = 1'b1,

In order to insure that there is only one acknowledgment for every request received, we’ll need to count requests and acknowledgments and compare our signals to these counters. F_LGDEPTH specifies the number of bits to be used for those counters.

	parameter				F_LGDEPTH	= 4,

We’re going to insist that no transaction remains stalled for more than some maximum number of clock cycles, F_AXI_MAXWAIT. This also keeps the design and traces moving during our proof. While the constraint placed upon the design as a result is somewhat artificial, you can adjust it to match what you would expect within your design environment.

	parameter	[(F_LGDEPTH-1):0]	F_AXI_MAXWAIT  = 12,

Our last parameter, F_AXI_MAXDELAY, is used to make certain that, following a request, the result will be returned to the AXI bus master within a given number of clock cycles. The number of cycles to wait is very implementation dependent, so it needs to be a configuration parameter. We set it here.

	parameter	[(F_LGDEPTH-1):0]	F_AXI_MAXDELAY = 12
	) (

In many ways, F_AXI_MAXDELAY=12 is overkill for the demonstration designs in the wishbone to AXI bridge repository we are taking our examples from. However, other designs have needed delays of 65 clocks or more, so this is an appropriate configuration parameter.

Let me add one other note on these two clock durations: the shorter F_AXI_MAXWAIT and F_AXI_MAXDELAY are, the faster your proof will complete.

Let’s now move on from the parameters within the formal property file to the inputs and outputs of the module itself. Since this formal property set is my own code rather than Xilinx’s, I’m also going to switch notations to one I am familiar with. Inputs to any core in my notation start with i_, outputs begin with an o_. Further, only constant values such as parameter or macros will use all capitals. Finally, since the core we will be writing is a formal property set, all of the interface wires will be inputs.

	input	wire			i_clk,	// System clock
	input	wire			i_axi_reset_n,

// AXI write address channel signals
	input	wire			i_axi_awready,//Slave is ready to accept
	input	wire	[AW-1:0]	i_axi_awaddr,	// Write address
	input	wire	[3:0]		i_axi_awcache,	// Write Cache type
	input	wire	[2:0]		i_axi_awprot,	// Write Protection type
	input	wire			i_axi_awvalid,	// Write address valid

// AXI write data channel signals
	input	wire			i_axi_wready,  // Write data ready
	input	wire	[DW-1:0]	i_axi_wdata,	// Write data
	input	wire	[DW/8-1:0]	i_axi_wstrb,	// Write strobes
	input	wire			i_axi_wvalid,	// Write valid

// AXI write response channel signals
	input	wire	[1:0]		i_axi_bresp,	// Write response
	input	wire			i_axi_bvalid,  // Write reponse valid
	input	wire			i_axi_bready,  // Response ready

// AXI read address channel signals
	input	wire			i_axi_arready,	// Read address ready
	input	wire	[AW-1:0]	i_axi_araddr,	// Read address
	input	wire	[3:0]		i_axi_arcache,	// Read Cache type
	input	wire	[2:0]		i_axi_arprot,	// Read Protection type
	input	wire			i_axi_arvalid,	// Read address valid

// AXI read data channel signals
	input	wire	[1:0]		i_axi_rresp,   // Read response
	input	wire			i_axi_rvalid,  // Read reponse valid
	input	wire	[DW-1:0]	i_axi_rdata,   // Read data
	input	wire			i_axi_rready,  // Read Response ready

Well, almost. We’re also going to create three outputs, as shown below, so that assertions may be connected to our various counters to constrain them to the implementation using them. Such constraints are necessary in order to pass induction, as we’ve discussed before.

	//
	output	reg	[(F_LGDEPTH-1):0]	f_axi_rd_outstanding,
	output	reg	[(F_LGDEPTH-1):0]	f_axi_wr_outstanding,
	output	reg	[(F_LGDEPTH-1):0]	f_axi_awr_outstanding
);

Since checking for transactions can be somewhat tedious below, I’ll declare some simple transaction abbreviations here. These are basically abbreviations for when both *VALID and *READY are true indicating that either a transaction or or an acknowledgment handshake completes.

	// wire	w_fifo_full;
	wire	axi_rd_ack, axi_wr_ack, axi_ard_req, axi_awr_req, axi_wr_req;
	//
	assign	axi_ard_req = (i_axi_arvalid)&&(i_axi_arready);
	assign	axi_awr_req = (i_axi_awvalid)&&(i_axi_awready);
	assign	axi_wr_req  = (i_axi_wvalid )&&(i_axi_wready);
	//
	assign	axi_rd_ack = (i_axi_rvalid)&&(i_axi_rready);
	assign	axi_wr_ack = (i_axi_bvalid)&&(i_axi_bready);

I’m also trying something new with this property set. Since bus slave properties are very similar to those for the master, save only that the assumptions and assertions are swapped, I’m going to create two macros: SLAVE_ASSUME and SLAVE_ASSERT. These are defined from the perspective of the slave to be assume and assert respectively. Within the master, these definitions will naturally swap.

`define	SLAVE_ASSUME	assume
`define	SLAVE_ASSERT	assert

Using a macro like this makes it easier to run meld on both slave and master property files when making updates. This way the actual logic differences stand out more. Interested in seeing how well this works? Just install meld, download the wb2axip repository, then cd into the bench/formal directory and run

% meld faxil_slave.v faxil_master.v

to see how easy it is to spot differences between the two cores.

Reset Properties

I’ve struggled a bit with the reset properties for AXI. Specifically, what core is it that actually creates the reset that needs to be verified here? That core should have the assertions applied to it. However, the reset is often defined by some other module within the design. Hence, we’ll either assert or assume the reset is initially set based instead on the F_OPT_ASSUME_RESET parameter from above.

	generate if (F_OPT_ASSUME_RESET)
	begin : ASSUME_INIITAL_RESET
		always @(*)
		if (!f_past_valid)
			assume(!i_axi_reset_n);
	end else begin : ASSERT_INIITAL_RESET
		always @(*)
		if (!f_past_valid)
			assert(!i_axi_reset_n);
	end endgenerate

Xilinx requires that the AXI reset be asserted for a minimum of 16 clock cycles. Our first step is to count the number of cycles the reset signal is active.

	initial	f_reset_length = 0;
	always @(posedge i_clk)
	if (i_axi_reset_n)
		// If ever the reset is released, "reset" the reset-length
		// counter back to zero.
		//
		f_reset_length <= 0;
	else if (!(&f_reset_length))
		// Otherwise, just quietly increment the counter until we get
		// to 15
		f_reset_length <= f_reset_length + 1'b1;

We can then make (assumptions) or assertions about the reset signal to make certain it is held long enough.

	generate if (F_OPT_ASSUME_RESET)
	begin : ASSUME_RESET
		// ...
	end else begin : ASSERT_RESET

		always @(posedge i_clk)
		if ((f_past_valid)&&(!$past(i_axi_reset_n))&&(!$past(&f_reset_length)))
			assert(!i_axi_reset_n);

		always @(*)
		if ((f_reset_length > 0)&&(f_reset_length < 4'hf))
			assert(!i_axi_reset_n);

	end endgenerate

Finally, now that we know our design meets its reset requirements, we can create some properties regarding what must happen as a result of a reset. Specifically, we’ll require that following any reset, the various *VALID flags should be set to zero.

We’re also going to apply this to the very first clock cycle of the design, by also checking for !f_past_valid and by applying these properties through initial statements. As you may recall, this was the issue the Xilinx core had above with its (missing) initial statements.

	// Nothing should be returned or requested on the first clock
	initial	`SLAVE_ASSUME(!i_axi_arvalid);
	initial	`SLAVE_ASSUME(!i_axi_awvalid);
	initial	`SLAVE_ASSUME(!i_axi_wvalid);
	//
	initial	`SLAVE_ASSERT(!i_axi_bvalid);
	initial	`SLAVE_ASSERT(!i_axi_rvalid);

	// Same thing, but following any reset as well
	always @(posedge i_clk)
	if ((!f_past_valid)||(!$past(i_axi_reset_n)))
	begin
		`SLAVE_ASSUME(!i_axi_arvalid);
		`SLAVE_ASSUME(!i_axi_awvalid);
		`SLAVE_ASSUME(!i_axi_wvalid);
		//
		`SLAVE_ASSERT(!i_axi_bvalid);
		`SLAVE_ASSERT(!i_axi_rvalid);
	end

Moving on to the response signals, S_AXI_BRESP for the write channel and S_AXI_RRESP for the read channel, we’ll note that the 2'b01 pattern is the only pattern disallowed by the AXI specification.

	always @(*)
	if (i_axi_bvalid)
		`SLAVE_ASSERT(i_axi_bresp != 2'b01); // Exclusive access not allowed
	always @(*)
	if (i_axi_rvalid)
		`SLAVE_ASSERT(i_axi_rresp != 2'b01); // Exclusive access not allowed

Stability Properties

The rule we discussed above was that the signals that are coupled with any transaction should be held constant as long as the transaction remains outstanding (i.e. valid but not ready). This is a basic handshake that we also required when building our WB properties. Let’s capture that handshake property here in this context.

Simply put using concurrent assertions, we could express this as:

	`SLAVE_ASSUME property (@(posedge i_clk)
		disable iff (!i_axi_reset_n)
		(i_axi_awvalid && !i_axi_awready)
		|=> i_axi_awvalid && ($stable(i_axi_awaddr)));

	`SLAVE_ASSUME property (@(posedge i_clk)
		disable iff (!i_axi_reset_n)
		(i_axi_wvalid && !i_axi_wready)
		|=> i_axi_wvalid && $stable(i_axi_wdata)
			&& $stable(i_axi_wstrb) );

	`SLAVE_ASSERT property (@(posedge i_clk)
		disable iff (!i_axi_reset_n)
		(i_axi_bvalid && !i_axi_bready)
		|=> i_axi_bvalid && $stable(i_axi_bresp));

	// ...

Alternately, in order to use the immediate assertions supported by the free version of SymbiYosys, we’ll need to put a little more work into this. First, we want to avoid the first clock period and any clock period following a reset. This is to make sure our properties deal with valid data.

	always @(posedge i_clk)
	if ((f_past_valid)&&($past(i_axi_reset_n)))
	begin

Now, for each channel, we’ll write out the properties in question. Basically if the *VALID was true on the previous cycle but the *READY was false, then the *VALID should remain true and the associated data should be stable.

For the write address channel, the first of five, this property looks like the following.

		// Write address channel
		if ((f_past_valid)&&($past(i_axi_awvalid))&&(!$past(i_axi_awready)))
		begin
			`SLAVE_ASSUME(i_axi_awvalid);
			`SLAVE_ASSUME($stable(i_axi_awaddr));
		end

		// Apply to all other incoming channels
	end

The other channel properties are nearly identical, so we’ll skip them for brevity here. The important part to remember is that we will assume properties of the input, and assert properties of our local state and any outputs. Hence, in this case we’ll assume the properties of the write address channel, the write data channel, and the read address channel, but assert properties of the two acknowledgment channels.

Maximum Delay

We said above that no channel should remain stalled for more than a finite number of clock cycles. Such a stall would be defined as *VALID && !*READY. Let’s check that property for each channel here, but only if we were given an F_AXI_MAXWAIT value greater than zero.

	generate if (F_AXI_MAXWAIT > 0)
	begin : CHECK_STALL_COUNT
		//
		//
		reg	[(F_LGDEPTH-1):0]	f_axi_awstall,
						f_axi_wstall,
						f_axi_arstall,
						f_axi_bstall,
						f_axi_rstall;

To create a check constraining how many clock cycles a design may be allowed to stall a channel, we’re going to have to first count the number of stalls.

I’ll show the write address channel stall count here, and skip the others for brevity again.

I should also mention, it took me several rounds to get this count just right. So, here’s the basic logic:

  1. Anytime we either reset the core, or anytime there’s no pending write request, or the write address request is accepted, the write address bus isn’t stalled and we set the counter back to zero. This much was straightforward, and matches my first draft.
		initial	f_axi_awstall = 0;
		always @(posedge i_clk)
		if ((!i_axi_reset_n)||(!i_axi_awvalid)||(i_axi_awready))
			f_axi_awstall <= 0;
  1. Likewise any time we are waiting for the other write channel, in this case the write data channel, to request a transaction we also set the counter to zero. This allows the Xilinx AXI-lite demo code to stall the bus as long as it wants while waiting for the other channel to synchronize.
		else if ((f_axi_awr_outstanding >= f_axi_wr_outstanding)
			&&(i_axi_awvalid && !i_axi_wvalid))
			// If we are waiting for the write channel to be valid
			// then don't count stalls
			f_axi_awstall <= 0;
  1. Here’s the part that caught me by surprise though: we only want to accumulate stalls on this request channel if the back end isn’t stalled. Hence if there’s no waiting acknowledgment, or likewise if the acknowledgment that is waiting has just been accepted, then and only then do we count a stall against the write address channel for not being ready.
		else if ((!i_axi_bvalid)||(i_axi_bready))
			f_axi_awstall <= f_axi_awstall + 1'b1;
  1. Finally, assert that the number of stalls is within our limit.
		always @(*)
			`SLAVE_ASSERT(f_axi_awstall < F_AXI_MAXWAIT);

		// The other channel stall counts are very similar

Why would we assert this? Because the stall signal, S_AXI_AWREADY, is an output of the slave core, and we always place assertions on outputs and assumptions on inputs.

Hence, if you look down through the property file a bit further, you’ll see an assumption made for the read acknowledgment channel. Why is this an assumption? Because it is dependent upon the S_AXI_BREADY input to the core.

		always @(*)
			`SLAVE_ASSUME(f_axi_rstall < F_AXI_MAXWAIT);

	end endgenerate

Of course, all of these assumptions will swap with their assertion counterparts when we go to the AXI-lite master property set.

Xilinx Constraints

Remember the two Xilinx constraints? The additional rules to make things work? Here they are written out.

  1. The address line will never be more than two clocks ahead of the write data channel, and

  2. The write data channel will never be more than one clock ahead of the address channel.

I found these rules in a DDR3 IP core module usage guide, though I can’t seem to find that guide right now. However, since they’ve helped make the various proofs complete, I’ve chosen to include these rules here.

Let’s express these as formal properties. First, if there was a write address request two clocks ago, and no intervening write data request, then we want to assume a write data request now.

Ok, not quite, that’s missing a key detail: it is possible that the write address request of two clocks ago followed a write data request. That means we’ll also have to check that the number of write data and write address requests were equal two clocks ago, or there had been more write address requests.

This is another one of those properties where a concurrent assertion would make the most sense,

	`SLAVE_ASSUME property (@(posedge i_clk)
		disable iff (!i_axi_reset_n)
		(i_axi_awvalid && !i_axi_wvalid)
			&&(f_axi_awr_outstanding>=f_axi_wr_outstanding)
		##1 (!i_axi_wvalid)
		|=> i_axi_wvalid);

We could also express this same property as an immediate assertion. It’s uglier and harder to read, but it still works well.

	always @(posedge i_clk)
	if ((i_axi_reset_n)&&($past(i_axi_reset_n))
		&&($past(i_axi_awvalid && !i_axi_wvalid,2))
			&&($past(f_axi_awr_outstanding>=f_axi_wr_outstanding,2))
			&&(!$past(i_axi_wvalid)))
		`SLAVE_ASSUME(i_axi_wvalid);

The second rule is simpler since it only covers two clock periods instead of three. It’s the same basic thing, just with the channels reversed and one less clock period.

	always @(posedge i_clk)
	if ((i_axi_reset_n)&&(!$past(i_axi_awvalid))&&($past(i_axi_wvalid))
			&&(f_axi_awr_outstanding < f_axi_wr_outstanding))
		`SLAVE_ASSUME(i_axi_awvalid);

Together these two properties will keep the two channels roughly synchronized with one another. Making the actual synchronization work within the peripheral code will still remain a challenge.

Compare the number of acknowledgments to requests

The next rule we want to check is that for every acknowledgment, there must have been one and only one request.

No matter how we do this, we’ll need to start by counting the number of outstanding requests. This count goes as follows: following any reset, the number of outstanding requests must be zero.

	initial	f_axi_awr_outstanding = 0;
	always @(posedge i_clk)
	if (!i_axi_reset_n)
		f_axi_awr_outstanding <= 0;

Likewise anytime we have accepted a request, or had an acknowledgment on the return channel accepted, but not both, the count will adjust.

	else case({ (axi_awr_req), (axi_wr_ack) })
		2'b10: f_axi_awr_outstanding <= f_axi_awr_outstanding + 1'b1;
		2'b01: f_axi_awr_outstanding <= f_axi_awr_outstanding - 1'b1;
		default: begin end
	endcase

Please notice that I didn’t use a pair of if statements here, such as if there’s been a write address channel request then increment the counter, else if there’s been a write response then decrement the counter. I’ve tried that approach several times in the past, but I always seem to get burned by it. Why? Because of the cases the if statements don’t cover, usually the case where there’s both a request and an acknowledgment on the same clock cycle.

Two other counters, f_axi_wr_outstanding based upon the write data channel and f_axi_rd_outstanding based upon the read channel, are defined similarly.

We can now start creating some properties using these count values. First, we want to make certain our counters never overflow.

	always @(posedge i_clk)
		`SLAVE_ASSERT(f_axi_wr_outstanding  < {(F_LGDEPTH){1'b1}});
	always @(posedge i_clk)
		`SLAVE_ASSERT(f_axi_awr_outstanding < {(F_LGDEPTH){1'b1}});
	always @(posedge i_clk)
		`SLAVE_ASSERT(f_axi_rd_outstanding  < {(F_LGDEPTH){1'b1}});

Second, in order to guarantee that the counters never overflow, we’ll need to insist that the channel stops making a request one clock earlier.

	always @(posedge i_clk)
	if (f_axi_awr_outstanding == { {(F_LGDEPTH-1){1'b1}}, 1'b0} )
		assert(!i_axi_awvalid);
	always @(posedge i_clk)
	if (f_axi_wr_outstanding == { {(F_LGDEPTH-1){1'b1}}, 1'b0} )
		assert(!i_axi_wvalid);
	always @(posedge i_clk)
	if (f_axi_rd_outstanding == { {(F_LGDEPTH-1){1'b1}}, 1'b0} )
		assert(!i_axi_arvalid);

You might notice that these are all a series of assertions–for both master and slave. They are not SLAVE_ASSERT()ions, but rather regular assertions. This somewhat violates our rule, that we only make assertions of local state and outputs. However, if an assumption is required to keep this number lower, that assumption should really exist within the implementation defined code. Hence we’ll just use regular assertions here.

Finally, to make certain that acknowledgments do follow requests, we can make a couple of assertions. The three counters above make these assertions really easy.

First, on any write acknowledgment, there must be at least one outstanding write address request that needs to be acknowledged. Likewise, there also needs to be one write data request that needs to be acknowledged.

	always @(posedge i_clk)
	if (i_axi_bvalid)
	begin
		`SLAVE_ASSERT(f_axi_awr_outstanding > 0);
		`SLAVE_ASSERT(f_axi_wr_outstanding  > 0);
	end

Notice here that I’m applying the test every time i_axi_bvalid is true, not every time axi_wr_ack, axi_awr_ack, nor every time S_AXI_BVALID && S_AXI_BREADY. In other words, before even attempting an acknowledgment, the respective counter should be greater than one.

A second thing to notice is that I’m not excepting the case where a request is being made on the same cycle. Such an acknowledgment, dependent only on a combinatorial expression of the inputs, is specifically disallowed by the AXI specification.

The assertion for the read channel is nearly identical to those for the write channel above.

	always @(posedge i_clk)
	if (i_axi_rvalid)
		`SLAVE_ASSERT(f_axi_rd_outstanding > 0);

This guarantees we’ll never respond to the bus unless a prior request has been made.

We haven’t yet guaranteed that every request will get a response. For that, we need to count the number of clock cycles following a request to when a response should taken place.

Maximum Response Delay Check

The maximum response delay check is just that: checking that every request gets a response within a maximum number of clock periods. This number of clock periods is captured by the configuration parameter F_AXI_MAXDELAY. Setting this parameter to zero will disable this check.

As with the other tests, we’ll start by counting how long a request remains unacknowledged or outstanding.

	generate if (F_AXI_MAXDELAY > 0)
	begin : CHECK_MAX_DELAY

		reg	[(F_LGDEPTH-1):0]	f_axi_wr_ack_delay,
						f_axi_rd_ack_delay;

This count is very similar to the stall count above. We’ll examine the read portion below, although the write count portion is similar. For a read, we’ll only count up if the reset is inactive, no acknowledgment is pending, and there exists an outstanding read that has not been acknowledged.

		initial	f_axi_rd_ack_delay = 0;
		always @(posedge i_clk)
		if ((!i_axi_reset_n)||(i_axi_rvalid)||(f_axi_rd_outstanding==0))
			f_axi_rd_ack_delay <= 0;
		else
			f_axi_rd_ack_delay <= f_axi_rd_ack_delay + 1'b1;

		// ...

We can then assert that the counter must remain less than the maximum acknowledgment delay.

		always @(*)
			`SLAVE_ASSERT(f_axi_rd_ack_delay < F_AXI_MAXDELAY);

		// ...
	end endgenerate

That’s the last of the safety properties necessary to determine that a core abides by the rules of AXI-lite.

When I originally started working with formal verification, I would stop once I’d finished writing my assertions and assumptions. I’ve since been burned multiply times by believing that a core worked when I’d somehow missed something internally, or perhaps assumed one property too many. For that reason, let’s add in some cover() properties.

Cover Properties

As a final property category, it’s important to have some assurance that a given AXI-lite slave core can handle a write request,

	always @(posedge i_clk)
	if (!F_OPT_NO_WRITES)
		cover((i_axi_bvalid)&&(i_axi_bready));

and a read request.

	always @(posedge i_clk)
	if (!F_OPT_NO_READS)
		cover((i_axi_rvalid)&&(i_axi_rready));
endmodule

Now, upon any SymbiYosys run in cover mode, the formal solver will find some path from reset, through either read or write request, through whatever operation the slave needs to do within its implementation, all the way to the acknowledgment being accepted. In many cases, this will also showcase the logic within the slave, giving you a trace you can use when debugging so that you can make sure you are implementing your logic properly.

Conclusion

I’d like to say that it only took me one weekend to build these properties. That’s roughly true. Interface property lists such as this one really aren’t that hard or difficult to build for a given application. Even better, the basic properties tend to remain the same from one application to the next. For example, we’re still using the same basic handshake properties here that we used for the WB bus, only now we are using different names for the signals.

However, it has taken some work on my part to build some example bus bridges and a demonstration AXI-lite slave core to give this property list some good exercise. Further, I’ve been using these properties to check the functionality of other AXI-slaves that I’ve found on-line, so I have some decent confidence that these properties work.

As we’ve seen above, these properties can be used to diagnose and then fix any AXI-lite core, such as the one produced by Vivado that we discussed above.

Even better, I’ve been able to use these properties to create a core that outperforms Xilinx’s AXI-lite demonstration core. This new example core can handle one read or write transaction request and thus acknowledgment on every clock, and it can keep this speed up indefinitely. Now, if only the interconnect would maintain that speed, you’d have a peripheral that runs a full twice as fast.

Just to give you a hint for what this core might do, here’s an example write trace from this new core.

Fig. 6. Write demonstration through an improved AXI-lite core
Fig. 7. Read demonstration through the improved AXI-lite core

Here’s an example read trace in Fig. 7 on the right.

Want to know how to build an AXI-lite core with this kind of throughput? Check out the buffered handshake approach to pipeline signaling and then stay tuned. That will likely be my next post on the topic of AXI-lite.

But what about the full AXI protocol? While I have a full Wishbone to full AXI bridge, I have yet to build a property file that would describe the full AXI protocol properly. Worse, I’ve put a lot of time into trying to build such a file. Too much time, in fact, so I really can’t afford to put much more time into it.

I’m sure I’ll get it soon enough, but given the amount of work it has taken me so far, it’s not very likely to be an open source core in the near future.